Before deciding to produce a custom inductor consider whether you have an alternative. If you are designing a filter circuit, for example, then below about 100kHz it becomes attractive to use either op-amp circuits or switched capacitor ICs instead. If an inductor has to be used then look to see if it can be obtained as an 'off the shelf' part from one of the usual distributors.
Here is a procedure that you can follow to design an inductor. It may not be the quickest way (it's somewhat 'trial and error') but it's easy to follow and understand -
See also ...
[
ESU Advisor index]
[Using the ESU coil winder]
[ Air coils]
[A guide to the terminology used in the science of magnetism]
[ Power loss in wound components]
[The force produced by a magnetic field]
[ Faraday's law]
[Bibliography]
[Acknowledgements]
Choosing a Core
The most important considerations
in core selection are usually -
Min H | Max H | Type of Core | Adjus- table? | High current? | Frequency limit |
---|---|---|---|---|---|
20 nano Henry | 1 micro Henry | Air cored, self supporting | Y | Y | 1GHz |
20 nano Henry | 100 micro Henry | Air cored, on former | N | Y | 500MHz |
100 nano Henry | 1 milli Henry | 'Slug' tuned open winding | Y | N | 500MHz |
10 micro Henry | 20 milli Henry | Ferrite ring | N | N | 500MHz |
20 micro Henry | 0.3 Henry | RM Ferrite Core | Y | N | 1MHz |
50 micro Henry | 1 Henry | EC or ETD Ferrite Core | N | Y | 1MHz |
1 Henry | 50 Henry | Iron | N | Y | 10kHz
|
Rings may be supplied with a coating of polyamide, polyurethane or other insulation. This helps to reduce self-capacitance by keeping the turns away from the ferrite (some grades have relative permittivities approaching 106).
Rings made from iron dust are also available. These can have saturation points of 1T or more but permeabilities of 30 or less are common for dust cores. Some grades will perform well into the VHF region. Magnetic field leakage is low.
Two basic types of RM cores are available: gapped and ungapped. Ungapped cores suitable for power applications are available with a different grade of ferrite which has a lower permeability but a higher value of saturation flux.
The size designations, RM6, RM7, RM10 etc. indicate that adjacent cores require a minimum spacing of 0.6, 0.7 or 1.0 inches on the PCB.
If using an ungapped EC core you can place thin pieces of plastic between each half to obtain a gap which can be made precisely the right width.
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Firstly, iron has high remnance (1.3 T) and coercivity (80 A m-1). This results in hysteresis power loss. The remedy is to include a small (about 3%) amount of silicon. This reduces the loss by at least a factor of 10.
Secondly, iron will conduct current. This is bad in a transformer core because eddy currents lead to further power loss. As a result transformers with iron cores are limited to audio frequencies or below. Even then, the iron is used in stacks of thin sheets (laminations).
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N = (109 × L / Al)1/2Example: We need to make an inductor using the standard example toroid core. How many turns do we need for 82 μH?
N = (109 × 82×10-6 / 2200)1/2 = 6.1 turnsIf the coil is air cored then you will need to re-arrange one of the traditional formulae for calculating the inductance of such coils from the dimensions and the number of turns.
N = Bsat×le/(µ×I) turnsExample: We need to make an inductor capable of carrying 1.3 amps using the standard example toroid. How many turns can be used?
N = 0.36 × 27.6×10-3 / (1.257×10-6 × 2490 × 1.3) = 2.4 turnsIn other words, we cannot put on more than two turns without hitting saturation! This gives us just 8.8 nH. Makes yer fink.
= Bsat×AeBy re-arranging Faraday's law,
N = ( E.dt ) / turnsExample: We need to make a transformer for a switching supply using the standard example toroid. The supply to the primary is 12 volts and the maximum 'on time' for the switch is 10 micro seconds. How many turns must we use?where E is the externally applied voltage.
= 0.36×19.4×10-6 = 6.98×10-6 webers
N = (12×10-5)/(6.98×10-6) = 17.2 turnsHere we must round up to 18 turns. With the current driven winding the flux increased with the number of turns but with a voltage driven winding the flux goes down with the number of turns. Honest. Please address any complaints on this issue to m.faraday@ri.ac.uk.
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There are some possible exceptions to this choice -
For self supporting coils this is usually decided on mechanical grounds; the larger the diameter of the coil the larger the diameter of wire used. A coil of 6 millimetre internal diameter might use 0.5 millimetre wire. Increase this pro rata if the coil takes heavy current.
For normal coils the diameter is chosen so that temperature rise and efficiency are both acceptable. Modern insulation materials are able to withstand temperatures so high that designing for tmax alone is probably not sensible. See the section on copper losses for more details.
You are encouraged to bring your own supplies of wire if using the
Workshop winding machines but if the quantity you require is small
(<20g) then ask a member of Workshop staff.
Handling wire
Always handle reels of thin enamel wire by the ends.
When such wire is used in equipment at high temperature or high voltage for
long periods of time then the acids present in fingerprints can lead to
insulation failure.
After using a reel please anchor the ends of the wire to the bobbin either using tape or by a hole or slot cut in the flange. Never simply tuck one turn under another; the next user won't realise what has happened and will attempt to unwind the free end - until the reel jams, usually leaving it a write-off.
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If you need many turns (>20) and wish to use one of the coil winders in the workshop then you must use a coil former.
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The practical inductor model includes a capacitor in parallel with the ideal inductor in order to represent stray capacitance between each turn and the turn next to it. There will also be distributed capacitance to any core that is used, and an exact model is too difficult to derive.
The consequence of this stray capacitance is that at some point (called the self resonant frequency) the impedance of the inductor will reach a peak. At higher frequencies the stray capacitance will become dominant and the impedance will begin to drop.
If you are deliberately using the inductor as part of a resonant circuit then it is important to note that the Q factor of a self resonant circuit is generally not high. Better values of Q can be obtained by choosing a smaller value of L and adding external capacitance to tune it. This behaviour is the reverse of that predicted by the simple formula for Q.
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It is usually essential to avoid reaching saturation since it is accompanied by a drop in inductance. In many circuits the rate at which current in the coil increases is inversely proprtional to inductance (I = V * T / L). Any drop in inductance therefore causes the current to rise faster, increasing the field strength and so the core is driven even further into saturation.
Core manufacturers normally specify the saturation flux density for the particular material used. You can also measure saturation using a simple circuit. There are two methods by which you can calculate flux if you know the number of turns and either -
If you find that saturation is likely then you might -
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You might object that this will also lead to a reduction in inductance which can only be compensated for by increasing the number of turns. With more turns the magneto-motive force will increase which will lead to higher flux once more. This argument is only partially correct because inductance increases according to the square of the number of turns whereas mmf is linearly proportional to N. Looked at another way, what you are doing is to shift the burden away from the core and onto the copper wire - after all, an air cored inductor can never saturate.
An analysis of the core and gap as a two component series circuit gives
µe = µr / (1 + (µr × lg / le))Where lg is the length of the gap. If you use a spacer then lg will be twice the spacer thickness because flux must cross the spacer twice in a complete circuit of the core.
The advantages of an air gap can be summarised
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This is impossible because if the first layer is wound from the left hand side of the coil former to the right hand side and has a normal 'right handed thread' (like a screw) then the second layer will have a 'left handed thread' as it moves back from the right side to the left. Since the turns on adjacent layers do not lie precisely parallel to one another, and must cross over at some point, they cannot always sit in the arrangement shown above. That said, the 'hop over' stretches may be quite short and much of the turn may still be in close contact with the turns below.
In practice you should allow for each layer to be separated by the whole thickness of the wire from the one underneath. The value of thickness used should be taken about 10% greater than the actual thickness to allow for irregularities. This applies only where the wire is fed on taking care that one turn is in close contact with the next. When thin wire (<0.2 millimetres) is used then this becomes impractical. About 15% should be added to the real diameter in the case of 'random wound' coils.
The wire sizes quoted in catalogues always refer to the diameter of the conductor. The enamel insulation increases this by about 10%.
Example - Core type RM7, conductor diameter 0.56 millimetres From data sheet - Length of winding space = 7 millimetres Height of winding space = 3.1 millimetres Nominal diameter including insulation = 0.56 × 1.10 = 0.62 Working diameter of wire = 0.62 × 1.10 = 0.68 millimetres Turns per layer = 7 / 0.68 = 10 Maximum number of layers = 3.1 / 0.68 = 4 Total = 10 × 4 = 40 turns.This method produces conservative estimates which allow for any lead-out wires and extra insulation that may be needed.
Usually it is only possible to keep close packing going for about 4 or 5 layers without the 'cross over' effect mentioned spoiling the winding. By placing a layer of polyester or masking tape round the coil after every 2 or 3 layers to 'stabilise' the winding then close packing can be continued indefinitely.
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Other sizes of wire and also Litz try
The Scientific Wire Co.
18, Raven Road
London E18 1HWTel. 0208 5050002
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1) Conventional enamel. This is usually dark brown in colour. In a production environment it is removed by a special rotary stripping machine. For prototype construction thick (>0.2mm) wire is best stripped with a scalpel blade. Rest the wire on a firm, flat surface and scrape the blade along at right angles to the wire.
Thinner wire is best stripped with fine sandpaper or emery cloth, although this is very slow. The process can be speeded up by first burning the enamel using a fine gas jet. This will leave a carbonized residue but this is much easier to sand away.
2) Self-fluxing enamel. This is usually pink or straw coloured. If you have a solder pot then simply dip the end of the wire in for a few seconds. The enamel will melt readily leaving you with a ready tinned end.
You can also remove the insulation if you have a soldering iron hot enough to melt it - about 400 centigrade. Most thermostatically controlled irons can be adjusted to run at this temperature. The joint will have been made correctly after the insulation is seen to 'bubble' for a second or two. When this happens the fumes emitted contain a small quantity of toluene di-isocyanate gas which is toxic and irritant. Use adequate ventilation. If this does not happen then the iron is not at the right temperature. Provided the soldering temperature is adequate, 'dry' joints are very rare.
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If you don't get the right inductance then remember that this is related to the square of the number of turns. If your inductance is 20% too low then you must increase the turns by just under 10%.
If you are building a power transformer then bear in mind the non-linearity of permeability.
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There is a longer list of references at http://www.mag-inc.com/techlit.html.
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